Complex-optical-field lidar system for range and vector velocity measurement

doi:10.1364/OE.20.025867

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Complex-optical-field lidar system for range and vector velocity measurement

Shuang Gao, Maurice O’Sullivan, and Rongqing Hui »View Author Affiliations

Optics Express, Vol. 20, Issue 23, pp. 25867-25875 (2012)
http://dx.doi.org/10.1364/OE.20.025867

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– Abstract
1. Introduction
2. System description
3. Experiment
4. Conclusion
– References and links

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Abstract

A coherent lidar system based on the measurement of complex optical field is demonstrated for the first time. An electro-optic in-phase/quadrature (I/Q) modulator is used in the lidar transmitter to realize carrier-suppressed complex optical field modulation in which the positive and the negative optical sidebands can carry independent modulation waveforms. A fiber-optic 90° hybrid is used in the lidar receiver for coherent heterodyne detection and to recover the complex optical field. By loading a constant modulation frequency on the lower optical sideband and a wideband linear frequency chirp on the upper sideband, vector velocity and target distance can be measured independently. The wide modulation bandwidth of this lidar system also enabled unprecedented range resolution and the capability of measuring high velocity unambiguously.

1. Introduction

Lidar is an important technique for the measurement of range, velocity and vibration, as well as atmospheric parameters [1

J. M. Vaughan, “Coherent laser spectroscopy and Doppler lidar sensing in the atmosphere,” Phys. Scr. T T78(1), 73–81 (1998). [CrossRef]

–4

X. Mao, D. Inoue, S. Kato, and M. Kagami, “Amplitude-modulated laser radar for range and speed measurement in car applications,” IEEE Trans. Intell. Transp. Syst. 13(1), 408–413 (2012). [CrossRef]

]. For velocity detection, one of the commonly used lidar schemes is pulsed Doppler lidar [3

M. Harris, R. I. Yong, F. Köpp, A. Dolfi, and J.-P. Cariou, “Wake vortex detection and monitoring,” Aerosp. Sci. Technol. 6(5), 325–331 (2002). [CrossRef]

A. D. Bouteyre, G. Canat, M. Valla, B. Augère, C. Besson, D. Goular, L. Lombard, J.-P. Cariou, A. Durecu, D. Fleury, L. Bricteux, S. Brousmiche, S. Lugan, and B. Macq, “Pulsed 1.5ìm lidar for axial aircraft wake vortex detection based on high brightness large-core fiber amplifier,” IEEE J. Sel. Top. Quantum Electron. 15, 441–450 (2009).

], where in the transmitter, optical pulses are intensity modulated at a constant frequency f_CW before launched out through a telescope. When the target is moving, the reflected signal acquires a Doppler frequency shift

f_{d} = 2 v / λ

, where v is the radial velocity of target and λ is the laser wavelength. This reflected optical signal is detected by an optical receiver, and the frequency

f = f_{C W} + f_{d}

carried on the signal can be obtained through a Fourier process so that the target velocity can be determined. The value of the Doppler frequency shift f_d can be either positive or negative depending on the direction of the velocity (moving towards or away from the observer). Theoretically, f_CW determines the maximum unambiguous velocity that could be measured without spectral aliasing of the received signal. Long optical pulses are usually desired to ensure the accuracy of velocity measurements as the resolution of velocity is determined by

v_{r e s} = λ / (2 T)

, where T is the pulse duration. On the other hand, it is well known that short optical pulses are required to achieve high range resolution if the target distance needs to be measured. This is because the target range information is obtained by measuring the roundtrip time of the optical pulse between the lidar and the target [4

]. Clearly, in a pulsed Doppler lidar system, a tradeoff has to be made between the velocity resolution and the range resolution.

In comparison to short pulsed lidar systems, FMCW lidar uses frequency chirped long optical pulses at much lower peak power and is able to provide large dynamic range while maintaining excellent resolution [6

C. J. Karlsson and F. Å. A. Olsson, “Linearization of the frequency sweep of a frequency-modulated continuous-wave semiconductor laser radar and the resulting ranging performance,” Appl. Opt. 38(15), 3376–3386 (1999). [CrossRef] [PubMed]

–8

M.-C. Amann, T. Bosch, M. Lescure, R. Myllylä, and M. Rioux, “Laser ranging: a critical reveiw of usual techniques for distance measurement,” Opt. Eng. 40(1), 10–19 (2001). [CrossRef]

]. For range measurements, saw-tooth or triangular waveforms are often used as the chirping signal in which the modulation frequency linearly shifts between the upper and the lower boundaries f₁ and f₂, as shown in Fig. 1 [8

M.-C. Amann, T. Bosch, M. Lescure, R. Myllylä, and M. Rioux, “Laser ranging: a critical reveiw of usual techniques for distance measurement,” Opt. Eng. 40(1), 10–19 (2001). [CrossRef]

D. Pierrottet, F. Amzajerdian, L. Petway, B. Barnes, G. Lockard, and M. Rubio, “Linear FMCW laser radar for precision range and vector velocity measurements,” Proc. Meter. Res. Soc. Symp. 1076 (2008).

]. When a saw-tooth waveform is used, on a stationary target, the target range R can be calculated through the measurement of the frequency difference between the transmitted and the returned modulation signal [7

P. Adany, C. Allen, and R. Hui, “Chirped lidar using simplified homodyne detection,” J. Lightwave Technol. 27(16), 3351–3357 (2009). [CrossRef]

]

f_{R} = \frac{(f_{2} - f_{1}) Δ t}{T} = 2 B R / (c T)

(1)

often referred to as the de-chirped frequency. In Eq. (1), T is the optical pulse duration,

B = f_{2} - f_{1}

is the chirping bandwidth, and c is the speed of light. The range resolution

R_{r e s} = c / 2 B

only depends on the chirping bandwidth. For a moving target, an additional Doppler frequency shift will be superimposed on f_R . This shift cannot be easily isolated so that a saw-tooth waveform is not suitable for the range and velocity measurement of moving targets.

Fig. 1 Illustration of linear FM chirped signal for FMCW lidar. T’ is the period and T is the pulse width.

The triangular chirping waveform illustrated in Fig. 1(b) contains both up-ramp and down-ramp segments., A lidar system using this chirp can detect range and velocity independently by calculating the two related frequencies

f_{R} = 4 R B / (T c) = (f_{R}^{+} + f_{R}^{-}) / 2

(2)

f_{d} = 2 ν / λ = (f_{R}^{+} - f_{R}^{-}) / 2

(3)

where,

f_{R}^{+}

and

f_{R}^{-}

are de-chirped frequencies measured during the up-ramp and the down-ramp sections, respectively. the velocity direction cannot be determined from a simple frequency analysis. Instead, de-chirping for up and down ramp sections must be performed separately within their respective temporal slots [9

In general, fine range resolution can be obtained with FMCW lidar by increasing chirping bandwidth. Whereas, a simple continuous wave at a single frequency is preferred in Doppler lidar for velocity measurements, which provides the most accurate results by avoiding possible complications of wideband modulation and the difficulty of maintaining the linearity of chirping. For simultaneous range and velocity measurements, a composite lidar waveform consisting of a wideband chirp and a single frequency tone may help optimize the overall performance.

In the lidar receiver [3

M. Harris, R. I. Yong, F. Köpp, A. Dolfi, and J.-P. Cariou, “Wake vortex detection and monitoring,” Aerosp. Sci. Technol. 6(5), 325–331 (2002). [CrossRef]

], coherent heterodyne detection is the most common choice because it has much higher receiver sensitivity compared with direct detection. It is also less susceptible to the phase noise of the optical carrier and the associated signal fading compared to homodyne detection. Heterodyne detection operates at an intermediate frequency f_IF, which is the frequency difference between the transmitted optical signal and the optical local oscillator (LO). A common method of creating this frequency shift in optics is to use an acousto-optic modulator (AOM). Practical AOMs can shift the optical frequency by as much as 1GHz. To avoid spectral aliasing using heterodyne detection, the maximum modulation bandwidth of the lidar system has to be lower than f_IF. This limits the range resolution. This limitation can be overcome by using an electro-optic I/Q modulator which is able to provide carrier-suppressed single-sideband modulation to generate a much higher f_IF for coherent heterodyne lidar system and achieve unprecedented range resolution [10

S. Gao and R. Hui, “Frequency-modulated continuous-wave lidar using I/Q modulator for simplified heterodyne detection,” Opt. Lett. 37(11), 2022–2024 (2012). [CrossRef] [PubMed]

Although using an I/Q modulator to generate multi-gigahertz intermediate frequency f_IF for heterodyne lidar helps improving range resolution, it does not make full use of the capability of an I/Q modulator. In fact, an I/Q modulator allows independent RF signals to be loaded onto the upper and the lower optical sidebands [11

Y. Zhang, M. O’Sullivan, and R. Hui, “Digital subcarrier multiplexing for flexible spectral allocation in optical transport network,” Opt. Express 19(22), 21880–21889 (2011). [CrossRef] [PubMed]

]. Generating high frequency f_IF in [10

S. Gao and R. Hui, “Frequency-modulated continuous-wave lidar using I/Q modulator for simplified heterodyne detection,” Opt. Lett. 37(11), 2022–2024 (2012). [CrossRef] [PubMed]

] only addresses one of the two optical sidebands. The other sideband is not used so that only range information was measured in a fiber delay line in reference [10

S. Gao and R. Hui, “Frequency-modulated continuous-wave lidar using I/Q modulator for simplified heterodyne detection,” Opt. Lett. 37(11), 2022–2024 (2012). [CrossRef] [PubMed]

In this paper we demonstrate that by applying a wide band chirping on the upper optical sideband and a constant frequency modulation on the lower optical sideband, it is possible to independently measure the target range and the velocity at the same time. A fiber-optic 90° hybrid was used in the coherent receiver to recover the complex optical spectrum composed of the in-phase and quadrature components. The resolution of velocity measurement is no longer dependent on the chirping bandwidth so that the system is more flexible and practical. The direction of velocity can be directly read from the spectrum of the received signal without the need of temporally truncated spectral analysis used in a conventional lidar system based on triangular chirping waveform. Thanks to the wide modulation bandwidth of the electro-optic I/Q modulator this lidar system allows wide chirping bandwidth on the upper sideband to ensure the fine range resolution and high enough modulation frequency on the lower sideband to allow the measurement of large unambiguous vector velocity, while maintaining a relatively simple optical system configuration. Because de-chirping in the receiver requires low-pass filtering [7

P. Adany, C. Allen, and R. Hui, “Chirped lidar using simplified homodyne detection,” J. Lightwave Technol. 27(16), 3351–3357 (2009). [CrossRef]

] after mixing, wide chirping bandwidth does not necessarily degrade lidar detection sensitivity.

2. System description

Figure 2 shows the block diagram of the proposed lidar system. The optical signal and the LO are split from the same CW laser source. The LO branch is directly connected to the receiver and the transmitted signal is modulated through an electro-optic I/Q modulator. The modulating RF signals from a digital arbitrary waveform generator (AWG) are fed to the I and the Q channels of the modulator independently. Optical carrier suppression and sideband rejection ratio are optimized by properly adjusting the DC bias of the modulator. As a result, a constant frequency modulation at f_CW is loaded onto the lower optical sideband and a wideband saw-tooth chirping signal is loaded onto the upper optical sideband. The modulated optical signal is amplified by an erbium doped fiber amplifier (EDFA), and a polarization controller (PC) behind the EDFA adjusts the state of polarization of the optical signal to match the principle axis of the 2x2 fiber-optic polarization beam splitter (PBS) connected to the telescope. A quarter wave plate is placed in front of the telescope to create a 90° polarization rotation for each roundtrip. Thus the optical signal reflected from the target and enters the telescope will pass through the PBS with minimum attenuation before it reaches the receiver through the adjacent fiber port. In the receiver, the optical signal is combined with the LO through a 2x2 fiber-optic 90° hybrid which allows the separation of the inphase and the quadrature components in the optical signal with two photodetectors. After photodetection, electrical signals are sampled by a pair of high speed analog-to-digital converters (ADC) before they are analyzed through digital signal processing.

Fig. 2 Block diagram of the proposed lidar system.

To create a wideband chirp waveform which linearly sweeps from f₁ to f₂ on the upper optical sideband, and a constant frequency modulation at f_CW on the lower optical sideband, the two voltage waveforms used to drive I and Q arms of the I/Q modulator are [10

S. Gao and R. Hui, “Frequency-modulated continuous-wave lidar using I/Q modulator for simplified heterodyne detection,” Opt. Lett. 37(11), 2022–2024 (2012). [CrossRef] [PubMed]

V_{I} (t) = V_{D} [\cos (2 π f_{1} t + π \frac{f_{2} - f_{1}}{T} t^{2}) - \sin (2 π f_{C W} t)]

(4)

V_{Q} (t) = V_{D} [- \sin (2 π f_{1} t + π \frac{f_{2} - f_{1}}{T} t^{2}) + \cos (2 π f_{C W} t)]

(5)

where, V_D is the amplitude of the driving voltage signal. When both intensity modulators (I and Q branches) inside the I/Q modulator are biased at null point, and the phase shifter is biased at the quadrature point, the optical field at the output of the modulator is [11

]

E_{0} = E_{s} [\sin (\frac{π V_{I} (t)}{V_{π}}) \cos (2 π f_{0} t) + \sin (\frac{π V_{Q} (t)}{V_{π}}) \sin (2 π f_{0} t)]

(6)

where f₀ is the optical frequency of the CW laser, E_s is the constant input optical field and V_π is the voltage required for the transfer function to change from the minimum to the maximum for each intensity modulator. For small-signal modulation,

V_{D} / V_{π} ≪ π

, Eq. (6) can be linearized to

E_{0} \approx E_{s} [\cos [2 π (f_{0} + f_{1} + \frac{f_{2} - f_{1}}{2 T} t) t] + \sin (2 π f_{0} t - 2 π f_{C W} t)]

(7)

This is a carrier suppressed optical signal with independent modulating signals carried on the upper and the lower sidebands. Since the optical LO is not modulated, its optical field can be expressed as,

E_{L O} = A_{L O} \cos (2 π f_{0} t)

(8)

where, A_LO is the field amplitude. The optical field reflected from the target E_sig contains a time delay Δt and a Doppler frequency shift f_d compared to the launched optical field given by Eq. (7), so that,

E_{s i g} = A_{s i g} [\cos [2 π (f_{0} + f_{1} + \frac{f_{2} - f_{1}}{2 T} (t - Δ t) + f_{d}) t] + \sin (2 π f_{0} t - 2 π f_{C W} t - 2 π f_{d} t)]

(9)

Where, A_sig is the amplitude of the reflected optical field. Sending E_LO and E_sig into the two input ports of the 90 degree optical hybrid, the optical fields E₁ and E₂ exiting the two output ports can be described by

(\begin{matrix} E_{1} \\ E_{2} \end{matrix}) = \frac{1}{\sqrt{2}} (\begin{matrix} 1 & \exp (j \frac{π}{4}) \\ \exp (j \frac{π}{4}) & 1 \end{matrix}) (\begin{matrix} E_{s i g} \\ E_{L O} \end{matrix})

(10)

Photocurrents of the two photodetectors after the 90° optical hybrid are,

I_{a r m 1} = ℜ {| E_{1} |}^{2} = ℜ A_{L O} A_{s i g} {\cos [2 π (f_{1} + \frac{f_{2} - f_{1}}{2 T} (t - Δ t) + f_{d}) t - \frac{π}{4}] - \sin (2 π f_{C W} t + 2 π f_{d} t + \frac{π}{4})}

(11)

I_{a r m 2} = ℜ {| E_{2} |}^{2} = ℜ A_{L O} A_{s i g} {- \sin [2 π (f_{1} + \frac{f_{2} - f_{1}}{2 T} (t - Δ t) + f_{d}) t - \frac{π}{4}] + \cos (2 π f_{C W} t + 2 π f_{d} t + \frac{π}{4})}

(12)

where

ℜ

is the responsivity of the photodetector, and terms due to direct detection have been neglected for simplicity. Because these two photocurrent signals represent the real and the imaginary parts of the optical signal, the complex optical signal can be recovered in the electrical domain as,

\begin{array}{l} I_{f i n a l} = I_{a r m 1} - j I_{a r m 2} \\ \begin{matrix}  \end{matrix} = ℜ A_{L O} A_{s i g} {\exp [j 2 π (f_{1} + \frac{f_{2} - f_{1}}{2 T} (t - Δ t) + f_{d}) t - j \frac{π}{4}] \\ \begin{matrix} - \exp [j (- 2 π f_{C W} t - 2 π f_{d} t + \frac{π}{4})] \end{matrix}} \end{array}

(13)

The complex optical spectrum can be obtained through a fast Fourier transform (FFT) on this composite electrical signal I_final, in which the positive and the negative sidebands represented by the 1st and the 2nd terms on the RHS of Eq. (13) are not redundant. Doppler frequency shift f_d can be obtained directly from the negative sideband, while the positive sideband corresponds to the time-delayed saw-tooth chirping signal. De-chirping can be applied by mixing the positive sideband with the original chirping waveform to find the de-chirped frequency f_R and the target range. In this process, the Doppler frequency shift f_d can be easily subtracted to make the range measurement accurate.

3. Experiment

The transmitter used in the lidar system experiment was built based on a Ciena commercial optical transmitter which was originally designed for 10Gb/s optical transmission with electronic domain pre-compensation [11

]. Two 21.42GS/s digital-to-analog converters (DAC) with 6-bit resolution were equipped in the transmitter, which converted the digital modulation signal to analog format to drive the two RF ports of the I/Q modulator. The amplitude of the RF modulating signal can be varied by adjusting the gain of the two RF power amplifiers after the DACs. This transmitter has a 15-bit long internal digital memory so that the maximum temporal length of the arbitrary waveform generated by this transmitter was 1.5298µs. The bandwidth of the I/Q modulator used in the experiment was 10GHz. An integrated tunable laser assembly (Emcore TTX1994) was used as the CW laser source with 100kHz spectral linewidth, The laser wavelength was set at 1549.65nm in the experiment.

The optical signal from the transmitter was collimated onto a spinning disc through free-space optics. The surface of the disc is covered with retro-reflective tape so that the reflected optical signal can be easily collected. The disc was placed approximately 1.6m away from the telescope. The velocity seen by the laser beam can be adjusted by changing either the beam position along the radius of the disc, or the angle between the laser beam and the disc surface normal. Note that the velocity is zero if the disc surface normal is in the same direction of the laser beam, the sign of the velocity seen by the laser can also be flipped through this angle change. The spinning speed of the disc is approximately 2316 rpm (revolutions per minute) and the beam position on the disc is about 4.5cm off the center.

In the receiver, two wideband photodiodes were used after the 90 degree optical hybrid both with 30GHz bandwidth. A real-time oscilloscope (LeCory 8600A) with 20Gs/s sampling rate and approximately 6GHz analog bandwidth was utilized as the ADCs after the RF pre-amplifiers which digitally record the two detected signals. Then the digital signals were processed using a MATLAB program to extract the velocity and range information.

To simultaneously measuring the speed and the distance, two different modulation signals were loaded independently onto the upper and the lower optical sidebands. The upper sideband was loaded with a saw-tooth linear chirping as shown in Fig. 1(a) with 4.3GHz chirping bandwidth. A raised cosine window function was applied to the chirping signal to minimize the edge effect on each optical pulse. The pulse repetition period was

T' = 1.5298 μ s

, and pulse duration was

T = 0.6884 μ s

. The lower sideband was loaded with a single frequency modulation at

f_{C W} = 5.3545 G H z

, which corresponds to a maximum measurable non-aliasing velocity of 4.149km/s. For the signal on the lower sideband, the pulse width equals to the repetition period T’ so that the amplitude of the sinusoid is constant. The selection of modulation frequency at

f_{C W} = 5.3545 G H z

minimizes the phase discontinuity between data frames. The dashed curve in Fig. 3 shows the signal optical spectrum measured by an optical spectrum analyzer (OSA) with 0.01 nm spectral resolution. The solid trace in Fig. 3 was the same optical spectrum but measured with a coherent heterodyne technique by mixing the optical signal with another narrow linewidth laser whose central frequency was approximately 6 GHz away from that of the signal laser. The heterodyne spectrum shown in Fig. 3 was acquired through an RF spectrum analyzer so that the spectral resolution is much better than that measured with the OSA. The optical spectrum in Fig. 3 clearly shows a constant frequency component on the left side for velocity measurement, a residual optical carrier in the middle, and a wideband frequency chirp on the right side for range measurement. In addition, the residual modulation sideband on the opposite side of the optical carrier is also visible, but with >20dB power suppression ratio. Note that there are also a few spectral lines in Fig. 3 which were generated from nonlinear mixing between the residual optical carrier, the single-tone modulation and its unsuppressed sideband. This is attributed to the nonlinear transfer function of the system as well as the saturation of the photodiode since the power of the optical LO in the heterodyne spectral measurement was relatively high.

Fig. 3 Signal optical spectrum measured with an OSA with 0.01nm resolution (dashed line) and with coherent heterodyne detection (solid line).

At the lidar receiver, the optical signal reflected from the spinning disc was combined with LO through the 90° optical hybrid. The two output ports are detected by two photodiodes, digitized and combined to reconstruct the complex optical field as described by Eq. (13). With the perspective of real-time lidar operation, we truncated the recorded time-domain digital signal into lengths equal to the pulse repetition time

T' = 1.5298 μ s

, corresponding to the update rate of approximately 653 MHz. This composite signal is converted into frequency domain through an FFT process. Figure 4 shows a typical spectrum of the complex electrical signals measured at the lidar receiver. This figure covering the full spectral window demonstrates the digital recovery of the complex optical field spectrum comparable to that shown in Fig. 3, and the two optical sidebands can be utilized for independent purposes.

Fig. 4 Power spectral density of the detected complex electrical signal described by Eq. (13).

Velocity detection is accomplished by measuring the Doppler induced frequency shift of the single-tone on the lower optical sideband. Figure 5 shows the expanded view at that single-tone for the target with a positive and a negative velocity by changing the orientation angle of the spinning disc. In the two measurements, both the radial position of the laser beam on the disc and the distance between the lidar and the disc remain unchanged. The solid line and the dashed line in Fig. 5 represent the spectra of the received signal with the target moving towards and away from the observer, respectively. Because of the Doppler effect, the measured frequency is different from the original single-tone modulation frequency of

f_{C W} = - 5.3545 G H z

, The precise target velocity information can be obtained by measuring this frequency shift. The bottom and the top horizontal axes of Fig. 5 indicate the frequency f and the corresponding velocity calculated from

v = (| f | - | f_{C W} |) λ / 2

. The target velocities indicated by the solid and the dashed spectra are + 5.81m/s and −7.62m/s, corresponding to the disc orientation angle of 32° and −44°, respectively. Based on the 3-dB width of the spectra, the resolution of the velocity measurement in this experiment is approximately 0.5m/s, which agrees with the theoretical value predicted by

v_{r e s} = λ / (2 T')

Fig. 5 Zoomed-in view at the single-tone modulation frequency for velocity measurement. Solid and dashed lines represent spectra measured when the target moves toward and away from the observer, respectively.

Figure 6 shows the de-chirped spectra for range measurements. De-chirping was performed by mixing the received signal shown on the upper sideband of Fig. 4 with the original chirping waveform. However, for a moving target, the Doppler-effect shifts the detected signal by a frequency f_d which is a function of the target velocity. Obviously this Doppler frequency shift has an impact on the de-chirping process. The solid and the dashed lines in Fig. 6 represent de-chirped spectra obtained for the target with the positive and the negative speed as discussed previously. The distance between the lidar transmitter and the target can be calculated by,

R = (f_{R} - f_{d}) c T / 2 B

(14)

Where f_R is the peak frequency of the de-chirped spectrum, f_d is the Doppler frequency shift which is obtained from the velocity measurement described above, and B is the chirping bandwidth. Note that in Fig. 6 there is an extra frequency component at

f_{c} = 0.43 G H z

in each spectrum but at a much lower amplitude. This is originated from the back reflection off the fiber APC (angled physical contact) terminal which leads to the telescope. Since optical signal reflected from the fiber terminal is not affected by the Doppler frequency shift caused by the target velocity, the peak frequency of this component is identical for the two measurements. In fact, the actual distance between the fiber terminal (at the telescope) and the target can simply be determined from the frequency difference between the spectral peaks caused by the target and the fiber terminal as

R' = (f_{R} - f_{c} - f_{d}) c T / 2 B

. This resulted in the target distances (from the fiber terminal) of

R' = 1.614 m

and

R' = 1.612 m

for the measurements with positive and negative velocities of the target, respectively. Apparently the location of the disc was slightly moved in the process of flipping its orientation angle. Based on the 3dB width of the de-chirped spectrum, the range resolution is determined as approximately 2.8cm. This roughly agrees with the calculated range resolution

R_{r e s} = c / 2 B = 3.49 c m

, where

R_{r e s}

is defined as the width between the minima on the two sides of the central peak.

Fig. 6 De-chirped signal spectra for distance measurements. Solid and dashed lines represent spectra measured when the target moves toward and away from the observer, respectively.

4. Conclusion

In this paper, we have demonstrated a coherent lidar system utilizing complex optical field to enhance its functionality and flexibility. An electro-optic I/Q modulator was used in the transmitter to generate the complex optical field modulation, which allowed two independent modulation waveforms to be loaded onto the lower and upper optical sidebands to achieve multiple functionalities. This complex optical field was recovered at the lidar receiver through a 90° optical hybrid. We have experimentally demonstrated the simultaneous detection of target range and vector velocity with high resolution. In comparison to a coherent heterodyne lidar using a conventional AOM as the frequency shifter, electro-optic I/Q modulator intrinsically has a much wider modulation bandwidth, so that it is able to provide unprecedented range resolution and the ability to detect high velocity without spectral aliasing. Because an additional degree of freedom is made available to the optical signal, the proposed technique can be applied to other advanced lidar detection schemes for enhanced functionalities. Note that the requirement of high speed digital electronics in the wideband Lidar proposed here may increase the cost of the system, and therefore a tradeoff between performance and cost has to be made depending on specific applications.

Acknowledgments

This work was supported in part by CIENA Corp, and by KU Transportation Research Institute (TRI). S. Gao acknowledges the financial support from China Scholarship Council (CSC).

References and links

1.	J. M. Vaughan, “Coherent laser spectroscopy and Doppler lidar sensing in the atmosphere,” Phys. Scr. T T78(1), 73–81 (1998). [CrossRef]
2.	C. J. Karlsson, F. Å. A. Olsson, D. Letalick, and M. Harris, “All-fiber multifunction continuous-wave coherent laser radar at 1.55um for range, speed, vibration, and wind measurements,” Appl. Opt. 39(21), 3716–3726 (2000). [CrossRef] [PubMed]
3.	M. Harris, R. I. Yong, F. Köpp, A. Dolfi, and J.-P. Cariou, “Wake vortex detection and monitoring,” Aerosp. Sci. Technol. 6(5), 325–331 (2002). [CrossRef]
4.	X. Mao, D. Inoue, S. Kato, and M. Kagami, “Amplitude-modulated laser radar for range and speed measurement in car applications,” IEEE Trans. Intell. Transp. Syst. 13(1), 408–413 (2012). [CrossRef]
5.	A. D. Bouteyre, G. Canat, M. Valla, B. Augère, C. Besson, D. Goular, L. Lombard, J.-P. Cariou, A. Durecu, D. Fleury, L. Bricteux, S. Brousmiche, S. Lugan, and B. Macq, “Pulsed 1.5ìm lidar for axial aircraft wake vortex detection based on high brightness large-core fiber amplifier,” IEEE J. Sel. Top. Quantum Electron. 15, 441–450 (2009).
6.	C. J. Karlsson and F. Å. A. Olsson, “Linearization of the frequency sweep of a frequency-modulated continuous-wave semiconductor laser radar and the resulting ranging performance,” Appl. Opt. 38(15), 3376–3386 (1999). [CrossRef] [PubMed]
7.	P. Adany, C. Allen, and R. Hui, “Chirped lidar using simplified homodyne detection,” J. Lightwave Technol. 27(16), 3351–3357 (2009). [CrossRef]
8.	M.-C. Amann, T. Bosch, M. Lescure, R. Myllylä, and M. Rioux, “Laser ranging: a critical reveiw of usual techniques for distance measurement,” Opt. Eng. 40(1), 10–19 (2001). [CrossRef]
9.	D. Pierrottet, F. Amzajerdian, L. Petway, B. Barnes, G. Lockard, and M. Rubio, “Linear FMCW laser radar for precision range and vector velocity measurements,” Proc. Meter. Res. Soc. Symp. 1076 (2008).
10.	S. Gao and R. Hui, “Frequency-modulated continuous-wave lidar using I/Q modulator for simplified heterodyne detection,” Opt. Lett. 37(11), 2022–2024 (2012). [CrossRef] [PubMed]
11.	Y. Zhang, M. O’Sullivan, and R. Hui, “Digital subcarrier multiplexing for flexible spectral allocation in optical transport network,” Opt. Express 19(22), 21880–21889 (2011). [CrossRef] [PubMed]

OCIS Codes
(040.2840) Detectors : Heterodyne
(120.4640) Instrumentation, measurement, and metrology : Optical instruments
(280.3640) Remote sensing and sensors : Lidar

ToC Category:
Remote Sensing

History
Original Manuscript: September 10, 2012
Revised Manuscript: October 20, 2012
Manuscript Accepted: October 22, 2012
Published: November 1, 2012

Citation
Shuang Gao, Maurice O’Sullivan, and Rongqing Hui, "Complex-optical-field lidar system for range and vector velocity measurement," Opt. Express 20, 25867-25875 (2012)
http://www.opticsinfobase.org/oe/abstract.cfm?URI=oe-20-23-25867

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References

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